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1 ? fn7061.3 caution: these devices are sensitive to electrosta tic discharge; follow proper ic handling procedures. 1-888-intersil or1-888-468-3774 | intersil (and design) is a registered trademark of intersil americas inc. copyright ? intersil americas inc. 2002-2006. all rights reserved. all other trademarks mentioned are the property of their respective owners. EL2250, el2450 125mhz single supply dual/quad op amps the EL2250/el2450 are part of a family of the electronics industries fastest single supply op amps available. prior single supply op amps have generally been limited to bandwidths and slew rates to that of the EL2250/el2450. the 125mhz bandwidth, 275v/s slew rate, and 0.05%/0.05 differential gain/differential phase makes this part ideal for single or dual supply video speed applications. with its voltage feedback architecture, this amplifier can accept reactive feedback networks, allowing them to be used in analog filtering applications. the inputs can sense signals below the bottom supply rail and as high as 1.2v below the top rail. connecting the load resistor to ground and operating from a single supply, the outputs swing completely to ground without saturating. the outputs can also drive to within 1.2v of the top rail. the EL2250/el2450 will output 100ma and will operate with single supply voltages as low as 2.7v, making them ideal for portable, low power applications. the EL2250/el2450 are available in pdip and so packages in industry standard pin outs. both parts operate over the industrial temperature range of -40c to +85c, and are part of a family of single supply op amps. for single amplifier applications, see the el2150/el2157. for dual and triple amplifiers with power down and output voltage clamps, see the el2257/el2357. features ? specified for +3v, +5v, or 5v applications ? large input common mode range 0v < v cm < v s -1.2v ? output swings to ground without saturating ? -3db bandwidth = 125mhz ? 0.1db bandwidth = 30mhz ? low supply current = 5ma (per amplifier) ? slew rate = 275v/s ? low offset voltage = 4mv max ? output current = 100ma ? high open loop gain = 80db ? differential gain = 0.05% ? differential phase = 0.05 ? pb-free plus anneal available (rohs compliant) applications ? video amplifiers ? pcmcia applications ?a/d drivers ? line drivers ? portable computers ? high speed communications ? rgb printers, fax, scanners ? broadcast equipment ? active filtering ordering information part number part marking tape & reel package pkg. dwg. # EL2250cn EL2250cn - 8 ld pdip mdp0031 EL2250cs 2250cs - 8 ld so mdp0027 EL2250cs-t7 2250cs 7? 8 ld so mdp0027 EL2250cs-t13 2250cs 13? 8 ld so mdp0027 EL2250csz (note) 2250csz - 8 ld so (pb-free) mdp0027 EL2250csz-t7 (note) 2250csz 7? 8 ld so (pb-free) mdp0027 EL2250csz-t13 (note) 2250csz 13? 8 ld so (pb-free) mdp0027 el2450cn el2450cn - 14 ld pdip mdp0031 el2450cs 2450cs - 14 ld so mdp0027 el2450cs-t7 2450cs 7? 14 ld so mdp0027 el2450cs-t13 2450cs 13? 14 ld so mdp0027 note: intersil pb-free plus anneal products employ special pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are rohs compliant and compatible with both snpb and pb-free soldering operations. intersil pb-free products are msl classified at pb-free peak reflow temperatures that meet or exceed the pb-free requirements of ipc/jedec j std-020. data sheet may 19, 2006
2 fn7061.3 may 19, 2006 pinouts EL2250c (8 ld so, pdip) top view el2450 (14 ld so, pdip) top view 1 2 3 4 8 7 6 5 - + - + a b outa ina- ina+ gnd vs+ outb inb- inb+ 1 2 3 4 14 13 12 11 5 6 7 10 9 8 outa ina- ina+ vs+ outd ind- ind+ gnd inb+ inb- outb inc+ inc- outc -+ - + -+ - + bc ad EL2250, el2450
3 fn7061.3 may 19, 2006 absolute maxi mum ratings (t a = 25c) supply voltage between v s and gnd . . . . . . . . . . . . . . . . . . +12.6v input voltage (in+, in-) . . . . . . . . . . . . . . . . . . . gnd-0.3v,v s +0.3v differential input voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .6v maximum output current. . . . . . . . . . . . . . . . . . . . . . . . . . . . . 90ma output short circuit duration. . . . . . . . . . . . . . . . . . . . . . . . (note 1) power dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . see curves storage temperature range . . . . . . . . . . . . . . . . . .-65c to +150c ambient operating temperature range . . . . . . . . . .-40c to +85c operating junction temperature . . . . . . . . . . . . . . . . . . . . . . . 150c caution: stresses above those listed in ?absolute maximum ratings? may cause permanent damage to the device. this is a stress o nly rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. important note: all parameters having min/max specifications are guaranteed. typical values are for information purposes only. u nless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: t j = t c = t a dc electrical specifications v s = +5v, gnd = 0v, t a = 25c, v cm = 1.5v, v out = 1.5v, unless otherwise specified. parameter description test conditions min typ max unit v os offset voltage -12 12 mv tcv os offset voltage temperature coefficient measured from t min to t max 10 v/c ib input bias current v in = 0v -5.5 -10 a i os input offset current v in = 0v -1200 150 1200 na tci os input bias current temperature coefficient measured from t min to t max 50 na/c psrr power supply rejection ratio v s = +2.7v to +12v 55 70 db cmrr common mode rejection ratio vcm = 0v to +3.8v 45 65 db vcm = 0v to +3.0v 50 70 db cmir common mode input range 0 v s -1.2 v r in input resistance common mode 1 2 m c in input capacitance so package 1 pf pdip package 1.5 pf r out output resistance a v = +1 40 m i s supply current (per amplifier) v s = +12v 5 6.5 ma psor power supply operating range 2.7 12.0 v dc electrical specifications v s = +5v, gnd = 0v, t a = 25c, v cm = +1.5v, v out = +1.5v, unless otherwise specified. parameter description test conditions min typ max unit avol open loop gain v s = +12v, v out = +2v to +9v, r l = 1k to gnd 60 80 db v out = +1.5v to +3.5v, r l = 1k to gnd 70 db v out = +1.5v to +3.5v, r l = 150 to gnd 60 db v op positive output voltage swing v s = +12v, a v = +1, r l = 1k to 0v 10.8 v v s = +12v, a v = +1, r l = 150 to 0v 9.6 10.0 v v s = 5v, a v = +1, r l = 1k to 0v 4.0 v v s = 5v, a v = +1, r l = 150 to 0v 3.4 3.8 v v s = +3v, a v = +1, r l = 150 to 0v 1.8 1.95 v v on negative output voltage swing v s = +12v, a v = +1, r l = 150 to 0v 5.5 8 mv v s = 5v, a v = +1, r l = 1k to 0v -4.0 v v s = 5v, a v = +1, r l = 150 to 0v -3.7 -3.4 v i out output current (note 1) v s = 5v, a v = +1, r l = 10 to 0v 75 100 ma v s = 5v, a v = +1, r l = 50 to 0v 60vma note: 1. internal short circuit protection circuitry has been bui lt into the EL2250/el2450; see the applications section EL2250, el2450
4 fn7061.3 may 19, 2006 ac electrical specifications v s = +5v, gnd = 0v, t a = 25c, v cm = +1.5v, v out = +1.5v, a v = +1, r f = 0 , r l = 150 to gnd pin, unless otherwise specified. (note 1) parameter description test conditions min typ max unit bw -3db bandwidth (v out = 400mv p-p ) v s = +5v, a v = +1, r f = 0 125 mhz v s = +5v, a v = -1, r f = 500 60 mhz v s = +5v, a v = +2, r f = 500 60 mhz v s = +5v, a v = +10, r f = 500 6mhz v s = +12v, a v = +1, r f = 0 150 mhz v s = +3v, a v = +1, r f = 0 100 mhz bw 0.1db bandwidth (v out = 400mv p-p ) v s = +12v, a v = +1, r f = 0 25 mhz v s = +5v, a v = +1, r f = 0 30 mhz v s = +3v, a v = +1, r f = 0 20 mhz gbwp gain bandwidth product v s = +12v, @ a v = +10 60 mhz pm phase margin r l = 1k , c l = 6pf 55 sr slew rate v s = +10v, r l = 150 , v out = 0v to +6v 200 275 v/s v s = +5v, r l = 150 , v out = 0v to +3v 300 v/s t r , t f rise time, fall time 0.1v step 2.8 ns os overshoot 0.1v step 10 % t pd propagation delay 0.1v step 3.2 ns t s 0.1% settling time v s = 5v, r l = 500 , a v = +1, v out = 3v 40 ns 0.01% settling time v s = 5v, r l = 500 , a v = +1, v out = 3v 75 ns dg differential gain (note 2) a v = +2, r f = 1k 0.05 % dp differential phase (note 2) a v = +2, r f = 1k 0.05 e n input noise voltage f = 10khz 48 nv/ hz i n input noise current f = 10khz 1.25 pa/ hz notes: 1. all ac tests are performed on a ?warmed up? part, except slew rate, which is pulse tested. 2. standard ntsc signal = 286mv p-p , f = 3.58mhz, as v in is swept from 0.6v to 1.314v; r l is dc coupled. EL2250, el2450
5 fn7061.3 may 19, 2006 typical performance curves non-inverting frequency response (gain) non-inverting frequency response (phase) 3db bandwidth vs temperature for non-inverting gains 3db bandwidth vs temperature for inverting gains inverting frequency response (phase) inverting frequency response (gain) frequency response for various r l frequency response for various c l non-inverting frequency response vs common mode voltage EL2250, el2450
6 fn7061.3 may 19, 2006 typical performance curves (continued) 3db bandwidth vs supply voltage for non-inverting gains frequency response for various supply voltages, a v = + 1 pssr and cmrr vs frequency psrr and cmrr vs die temperature frequency response for various supply voltages, a v = + 2 3db bandwidth vs supply voltage for inverting gains open loop gain and phase vs frequency open loop voltage gain vs die temperature closed loop output impedance vs frequency EL2250, el2450
7 fn7061.3 may 19, 2006 typical performance curves (continued) large signal step response, v s = +3v large signal step response, v s = +5v large signal step response, v s = +12v small signal step response large signal step response, v s = 5v slew rate vs temperature settling time vs settling accuracy voltage and current noise vs frequency EL2250, el2450
8 fn7061.3 may 19, 2006 typical performance curves (continued) differential gain for single supply operation differential phase for single supply operation differential gain and phase for dual supply operation 2nd and 3rd harmonic distortion vs frequency 2nd and 3rd harmonic distortion vs frequency 2nd and 3rd harmonic distortion vs frequency output voltage swing vs frequency for thd < 0.1% output voltage swing vs frequency for unlimited distortion output current vs die temperature EL2250, el2450
9 fn7061.3 may 19, 2006 typical performance curves (continued) supply current vs supply voltage (per amplifier) supply current vs die temperature (per amplifier) input resistance vs die temperature offset voltage vs die temperature (4 samples) input bias current vs input voltage input offset current and input bias current vs die temperature positive output voltage swing vs die temperature, r l = 150 to gnd negative output voltage swing vs die temperature, r l = 150 to gnd channel to channel isolation vs frequency package power dissipation vs ambient temp. semi g42-88 single layer test board ambient temperature (c) power dissipation (w) 1.8 1.6 1.4 1.2 1 0.8 0.6 0.4 0.2 0 0255075100125150 85 1.54w 1.25w p d i p 1 4 j a = 8 1 c / w p d i p 8 j a = 1 0 0 c / w package power dissipation vs ambient temp. jedec jesd51-3 low effective thermal conductivity test board ambient temperature (c) power dissipation (w) 1.2 1 0.8 0.6 0.4 0.2 0 0 25 50 75 100 125 150 85 1.042w 781w s o 1 4 j a = 1 2 0 c / w s o 8 j a = 1 6 0 c / w EL2250, el2450
10 fn7061.3 may 19, 2006 simplified schematic applications information product description the EL2250/el2450 are part of a family of the industries fastest single supply operational amplifiers. connected in voltage follower mode, their -3db bandwidth is 125mhz while maintaining a 275v/s slew rate. with an input and output common mode range that includes ground, these amplifiers were optimized for single supply operation, but will also accept dual supplies. they operate on a total supply voltage range as low as +2.7v or up to +12v. this makes them ideal for +3v applications, especially portable computers. while many amplifiers claim to operate on a single supply, and some can sense ground at their inputs, most fail to truly drive their outputs to ground. if they do succeed in driving to ground, the amplifier often satu rates, causing distortion and recovery delays. however, spec ial circuitry built into the EL2250/el2450 allows the output to follow the input signal to ground without recovery delays. power supply bypassing and printed circuit board layout as with any high-frequency device, good printed circuit board layout is necessary for optimum performance. ground plane construction is highly recommended. lead lengths should be as short as possible. the power supply pins must be well bypassed to reduce the risk of oscillation. the combination of a 4.7f tantalum capacitor in parallel with a 0.1f ceramic capacitor has been shown to work well when placed at each supply pin. for single supply operation, where the gnd pin is connected to the ground plane, a single 4.7f tantalum capacitor in parallel with a 0.1f ceramic capacitor across the v s + and gnd pins will suffice. for good ac performance, parasitic capacitance should be kept to a minimum. ground pl ane construction should be used. carbon or metal-film re sistors are acceptable with the metal-film resistors giving slightly less peaking and bandwidth because of their additional series inductance. use of sockets, particularly for the so package should be avoided if possible. sockets add parasitic inductance and capacitance which will result in some additional peaking and overshoot. supply voltage range and single-supply operation the EL2250/el2450 have been designed to operate with supply voltages having a span of greater than 2.7v, and less than 12v. in practical terms, this means that the EL2250/el2450 will operate on dual supplies ranging from 1.35v to 6v. with a single-supply, the EL2250/el2450 will operate from +2.7v to +12v. performance has been optimized for a single +5v supply. pins 8 and 4 are the power supply pins on the EL2250. the positive power supply is connected to pin 8. when used in single supply mode, pin 4 is connected to ground. when used in dual supply mode, the negative power supply is connected to pin 4. pins 4 and 11 are the power supply pins on the el2450. the positive power supply is connected to pin 4. when used in single supply mode, pin 11 is connected to ground. when used in dual supply mode, the negative power supply is connected to pin 11. as supply voltages continue to decrease, it becomes necessary to provide input an d output voltage ranges that can get as close as possible to the supply voltages. the EL2250/el2450 have an input voltage range that includes the negative supply and extends to within 1.2v of the positive supply. so, for example, on a single +5v supply, the EL2250/el2450 have an input range which spans from 0v to 3.8v. EL2250, el2450
11 fn7061.3 may 19, 2006 the output range of the EL2250/ el2450 is also quite large. it includes the negative rail, and extends to within 1v of the top supply rail with a 1k load. on a +5v supply, the output is therefore capable of swinging from 0v to +4v. on split supplies, the output will swing 4v. if the load resistor is tied to the negative rail and split supplies are used, the output range is extended to the negative rail. choice of feedback resistor, r f the feedback resistor forms a pole with the input capacitance. as this pole becomes larger, phase margin is reduced. this increases ringing in the time domain and peaking in the frequency domain. therefore, r f has some maximum value which should not be exceeded for optimum performance. if a large value of r f must be used, a small capacitor in the few picofarad range in parallel with r f can help to reduce this ringing and peaking at the expense of reducing the bandwidth. as far as the output stage of the amplifier is concerned, r f +r g appear in parallel with r l for gains other than +1. as this combination gets smaller, the bandwidth falls off. consequently, r f has a minimum value that should not be exceeded for optimum performance. for a v = +1, r f = 0 is optimum. for a v = -1 or +2 (noise gain of 2), optimum response is obtained with r f between 500 and 1k . for a v = -4 or +5 (noise gain of 5), keep r f between 2k and 10k . video performance for good video performance, an amplifier is required to maintain the same output impedance and the same frequency response as dc levels are changed at the output. this can be difficult when driving a standard video load of 150 , because of the change in output current with dc level. differential gain and differential phase for the EL2250/el2450 are specified wit h the black level of the output video signal set to +1.2v. this allows ample room for the sync pulse even in a gain of +2 configuration. this results in dg and dp specificat ions of 0.05% and 0.05 while driving 150 at a gain of +2. setting the black level to other values, although acceptable, will compromise peak performance. for example, looking at the single supply dg and dp curves for r l = 150 , if the output black level clamp is reduced from 1.2v to 0. 6v dg/dp will increase from 0.05%/0.05 to 0.08%/0.25 note that in a gain of +2 configuration, this is the lowest black level allowed such that the sync tip doesn?t go below 0v. if your application requires that the output goes to ground, then the output stage of the EL2250/el2450, like all other single supply op amps, requires an external pull down resistor tied to ground. as mentioned above, the current flowing through this resistor becomes the dc bias current for the output stage npn transistor . as this current approaches zero, the npn turns off, and dg and dp will increase. this becomes more critical as the load resistor is increased in value. while driving a light load, such as 1k , if the input black level is kept above 1.25v, dg and dp are a respectable 0.03% and 0.03. for other biasing conditions see the differential gain and differential phase vs. input voltage curves. output drive capability in spite of their moderately low 5ma of supply current, the EL2250/el2450 are capable of providing 100ma of output current into a 10 load, or 60ma into 50 . with this large output current capability, a 50 load can be driven to 3v with v s = 5v, making it an excellent choice for driving isolation transformers in te lecommunications applications. driving cables and capacitive loads when used as a cable driver, double termination is always recommended for reflection-free performance. for those applications, the back-termination series resistor will de- couple the EL2250/el2450 from the cable and allow extensive capacitive drive. however, other applications may have high capacitive loads without a back-termination resistor. in these applications, a small series resistor (usually between 5 and 50 ) can be placed in series with the output to eliminate most peaking. the gain resistor (r g ) can then be chosen to make up for any gain loss which may be created by this additiona l resistor at the output. video sync pulse remover application all cmos analog to digital converters (a/ds) have a parasitic latch-up problem when subjected to negative input voltage levels. since the sync tip contains no useful video information and it is a negative going pulse, we can chop it off. figure 1 shows a unity gain connected amplifier a of an EL2250. figure 2 shows the complete input video signal applied at the input, as well as the output signal with the negative going sync pulse removed. figure 1. EL2250, el2450
12 fn7061.3 may 19, 2006 short circuit current limit the EL2250/el2450 have internal short circuit protection circuitry that protect it in the event of its output being shorted to either supply rail. this limit is set to around 100ma nominally and reduces with incr easing junction temperature. it is intended to handle temp orary shorts. if an output is shorted indefinitely, the power dissipation could easily increase such that the part will be destroyed. maximum reliability is maintained if the output current never exceeds 90ma. a heat sink may be required to keep the junction temperature below absolute ma ximum when an output is shorted indefinitely. power dissipation with the high output drive ca pability of the EL2250/el2450, it is possible to exceed the 150c absolute maximum junction temperature under certain load current conditions. therefore, it is important to calculate the maximum junction temperature for the application to determine if power-supply voltages, load conditions, or package type need to be modified for the EL2250/el2450 to remain in the safe operating area. the maximum power dissipation allowed in a package is determined according to [1]: where: t jmax = maximum junction temperature t amax = maximum ambient temperature ja = thermal resistance of the package pd max = maximum power dissipation in the package. the maximum power dissipation actually produced by an ic is the total quiescent supply current times the total power supply voltage, plus the power in the ic due to the load, or [2]: where: n = number of amplifiers v s = total supply voltage i smax = maximum supply current per amplifier v out = maximum output voltage of the application r l = load resistance tied to ground if we set the two pd max equations, [1] & [2], equal to each other, and solve for v s , we can get a family of curves for various loads and output voltages according to [3]: figures 3 through 6 below show total single supply voltage v s vs. r l for various output voltage swings for the pdip and so packages. the curves assume worst case conditions of t a = +85c and i s = 6.5ma per amplifier. figure 2. pd max t jmax t amax ? ja -------------------------------------------- - = pd max nv s i smax v s v out ? () v out r l --------------- - + ?? ?? ?? = v s r l t jmax t amax ? () n ja --------------------------------------------------------------- v out () + is r l () v out + ------------------------------------------------------------------------------------------ - = EL2250, el2450
13 fn7061.3 may 19, 2006 EL2250 single supply voltage vs r load for various v out (pdip package) figure 3. EL2250 single supply voltage vs r load for various v out (so package) figure 4. el2450 single supply voltage vs r load for various v out (pdip package) figure 5. el2450 single supply voltage vs r load for various v out (so package) figure 6. EL2250, el2450
14 fn7061.3 may 19, 2006 EL2250/el2450 macromodel (one amplifier) * revision a, april 1996 * pin numbers reflect a standard single op amp. * connections: +input * | -input * | | +vsupply * | | | -vsupply * | | | | output .subckt EL2250/el 3 2 7 4 6 * * input stage * i1 7 10 250a i2 7 11 250a r1 10 11 4k q1 12 2 10 qp q2 13 3 11 qpa r2 12 4 100 r3 13 4 100 * * second stage & compensation * gm 15 4 13 12 4.6m r4 15 4 15meg c1 15 4 0.36pf * * poles * e1 17 4 15 4 1.0 r6 17 25 400 c3 25 4 1pf r7 25 18 500 c4 18 4 1pf * * output stage * i3 20 4 1.0ma q3 7 23 20 qn q4 7 18 19 qn q5 7 18 21 qn q6 4 20 22 qp q7 7 23 18 qn d1 19 20 da r8 21 6 2 r9 22 6 2 r10 18 21 10k r11 7 23 100k d2 23 24 da d3 24 4 da d4 23 18 da * * power supply current * ips 7 4 3.2ma * * models * .model qn npn(is=800e -18 bf=150 tf=0.02ns) .model qpa pnp(is=810 e-18 bf=50 tf=0.02ns) .model qp pnp(is=800e-18 bf=54 tf=0.02ns) .model da d(tt=0ns) .ends EL2250, el2450
15 all intersil u.s. products are manufactured, asse mbled and tested utilizing iso9000 quality systems. intersil corporation?s quality certifications ca n be viewed at www.intersil.com/design/quality intersil products are sold by description only. intersil corpor ation reserves the right to make changes in circuit design, soft ware and/or specifications at any time without notice. accordingly, the reader is cautioned to verify that data sheets are current before placing orders. information furnishe d by intersil is believed to be accurate and reliable. however, no responsibility is assumed by intersil or its subsidiaries for its use; nor for any infringements of paten ts or other rights of third parties which may result from its use. no license is granted by implication or otherwise under any patent or patent rights of intersil or its subsidiari es. for information regarding intersil corporation and its products, see www.intersil.com fn7061.3 may 19, 2006 EL2250/el2450 macromodel (one amplifier) EL2250, el2450

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